Input voltage sensor responsive to load conditions

ABSTRACT

A power converter controller includes a switch driver circuit coupled to generate a drive signal to control switching of a power switch to control a transfer of energy from an input of the power converter to an output of the power converter. An input sense circuit is coupled to receive an input sense signal representative of the input of a power converter. A sense enable circuit is coupled to receive the drive signal to generate a sense enable signal to control the input sense circuit in response to the drive signal. The sense enable signal is coupled to control the input sense circuit to sense the input sense signal continuously in response to a first load condition, and sense the input sense signal only during a fraction of a switching period of the power switch in response to a second load condition.

BACKGROUND INFORMATION

1. Field of the Disclosure

The present invention is related to power converters. More specifically,the present invention is related to power converters that operate withhigh efficiency at light loads.

2. Background

Controllers for off-line power converters often must measure the inputvoltage to perform functions such as under-voltage detection andover-voltage protection. Off-line power converters typically receive aninput voltage that is greater than 100 volts ac. Since the ac voltagevaries periodically between a peak positive value and a peak negativevalue at the frequency of the power line, the ac line voltage istypically represented numerically as a root mean square (rms) value of asine wave. The rms value of the ac voltage is the magnitude of the peakvoltage divided by the square root of two. For example, in the UnitedStates the common household voltage is 120 volts ac with a peak value of169.7 volts. In many other parts of the world, the common householdvoltage is 240 volts ac with a peak value of 339.4 volts. The ac rmsvoltage is equivalent to a dc voltage of the same numeric value whenboth are applied to the same resistive load such as an incandescentlamp. Transient disturbances and faults on the power line canmomentarily raise the voltage to substantially higher values.

Off-line power converters typically rectify the ac input voltage toobtain an unregulated dc input voltage that is then converted to a lowerregulated dc voltage. The maximum value of the unregulated dc inputvoltage is approximately the peak value of the ac input voltage.Semiconductor components in the power converter may need to withstandvoltages that are substantially greater than the peak of the ac inputvoltage when the converter is operating. Therefore, it is necessary forcontrollers of power converters to measure the input voltage so that thecomponents may be protected from damage due to excessively high voltage.A controller may halt operation of the converter to prevent damage whenthe input voltage goes higher than a threshold value.

Circuits that measure an input voltage typically do so by using apotential divider across the input to provide a known fraction of theinput voltage that is low enough for the measurement circuit to handle.In order to reduce power consumption, the components of the divider areselected to take no more current from the input than necessary. Toreduce power consumption further and to reduce the number of components,a current that represents the input voltage can be used instead of apotential divider. However, the current needs to be large enough toguarantee a reliable measurement in the presence of noise. The powertaken from the source of input voltage is proportional to the product ofthe voltage and the current. Since the peak value of the ac input may behundreds of volts, even the smallest current acceptable for reliablemeasurement can still result in a significant loss of power, especiallywhen the power converter has a light load or no load. Power convertersneed a controller that can sense the input voltage reliably with lowpower consumption.

BRIEF DESCRIPTION OF THE DRAWINGS

Non-limiting and non-exhaustive embodiments of the present invention aredescribed with reference to the following figures, wherein likereference numerals refer to like parts throughout the various viewsunless otherwise specified.

FIG. 1 is a schematic diagram of an example power converter including acontroller that senses an input voltage in accordance with the teachingsof the present invention.

FIG. 2 is a functional block diagram of an example power convertercontroller illustrating elements of a load-selective input voltagesensor in accordance with the teachings of the present invention.

FIG. 3 is a timing diagram showing example waveforms that illustrate theoperation of the example load-selective input voltage sensor shown inFIG. 2 in accordance with the teachings of the present invention.

FIG. 4 is a graph showing an example relationship between the length oftime that the input voltage is not being sensed and the length of timethat the power switch is off in the example power converter of FIG. 1 inaccordance with the teachings of the present invention.

FIG. 5 is a functional block diagram of an example power convertercontroller illustrating elements of an alternative input voltage sensorin accordance with the teachings of the present invention.

FIG. 6 is a functional block diagram of an example power convertercontroller illustrating elements of another alternative input voltagesensor in accordance with the teachings of the present invention.

FIG. 7 is a flow diagram that illustrates an example process for sensingan input voltage in accordance with teachings of the present invention.

FIG. 8 is a schematic diagram of an example power converter including acontroller that senses a switching voltage representative of a dc inputvoltage in addition to sensing an ac input voltage in accordance withthe teachings of the present invention.

FIG. 9 is a schematic diagram of an example power converter controllerillustrating elements of an input voltage sensor that includes anoptional element to discharge stray capacitance in accordance with theteachings of the present invention.

Corresponding reference characters indicate corresponding componentsthroughout the several views of the drawings. Skilled artisans willappreciate that elements in the figures are illustrated for simplicityand clarity and have not necessarily been drawn to scale. For example,the dimensions of some of the elements in the figures may be exaggeratedrelative to other elements to help to improve understanding of variousembodiments of the present invention. Also, common but well-understoodelements that are useful or necessary in a commercially feasibleembodiment are often not depicted in order to facilitate a lessobstructed view of these various embodiments of the present invention.

DETAILED DESCRIPTION

In the following description, numerous specific details are set forth inorder to provide a thorough understanding of the present invention. Itwill be apparent, however, to one having ordinary skill in the art thatthe specific detail need not be employed to practice the presentinvention. In other instances, well-known materials or methods have notbeen described in detail in order to avoid obscuring the presentinvention.

Reference throughout this specification to “one embodiment”, “anembodiment”, “one example” or “an example” means that a particularfeature, structure or characteristic described in connection with theembodiment or example is included in at least one embodiment of thepresent invention. Thus, appearances of the phrases “in one embodiment”,“in an embodiment”, “one example” or “an example” in various placesthroughout this specification are not necessarily all referring to thesame embodiment or example. Furthermore, the particular features,structures or characteristics may be combined in any suitablecombinations and/or subcombinations in one or more embodiments orexamples. Particular features, structures or characteristics may beincluded in an integrated circuit, an electronic circuit, acombinational logic circuit, or other suitable components that providethe described functionality. In addition, it is appreciated that thefigures provided herewith are for explanation purposes to personsordinarily skilled in the art and that the drawings are not necessarilydrawn to scale.

The schematic diagram of FIG. 1 shows the salient features of oneexample of an ac-dc power converter 100 (ac input, dc output) receivingan ac input voltage V_(AC) 102 that has a substantially sinusoidalwaveform with a period T_(L). The ac line period T_(L) is the reciprocalof the ac line frequency. The standard ac line frequency is nominallyeither 50 hertz or 60 hertz, depending on the country and location ofthe power system. Power converters designed for worldwide operationtypically accept ac line frequencies between 47 hertz and 63 hertz,corresponding to ac line periods between approximately 21 millisecondsand 16 milliseconds, respectively. A controller 142 in the example powerconverter of FIG. 1 includes an input voltage sensor in accordance withthe teaching of the present invention. The example ac-dc power converterof FIG. 1 provides a substantially dc output voltage V_(O) 124 and asubstantially dc output current I_(O) 126 to a load 128.

The example power converter of FIG. 1 is known as a flyback powerconverter because of its particular circuit topology. A power converterthat is controlled to produce a regulated output is sometimes called aregulated power supply. A flyback converter that produces a regulatedoutput is sometimes called a flyback power supply. Those skilled in theart will appreciate that examples in accordance with the teachings ofthe present invention described in this disclosure is not limited topower converters that use a particular circuit topology, and that anytype of power converter that operates from either an ac input voltage orfrom a dc input voltage may benefit from examples in accordance with theteachings of the invention.

In the example power converter of FIG. 1, a full-wave bridge rectifier104 receives ac input voltage V_(AC) 102 between line input terminal L150 and neutral input terminal N 152 to produce a dc voltage V_(BULK)108 on an input capacitor C1 106. Dc voltage V_(BULK) 108 is positivewith respect to an input return 114, and has a time varying component attwice the frequency (half the period) of the ac line due to energy beingremoved from the capacitor by the power converter between peaks of theline voltage waveform 102. The maximum value of the bulk voltageV_(BULK) 108 is approximately the peak magnitude of the ac input voltageV_(AC) 102. The peaks of rectified voltage V_(BULK) 108 in the exampleof FIG. 1 are coincident with the positive and negative peaks of the acinput voltage V_(AC) 102. The minimum value of the bulk voltage V_(BULK)108 is substantially greater than zero when the ac input voltage V_(AC)102 is present.

The dc voltage V_(BULK) 108 in the example of FIG. 1 is coupled to acoupled inductor T1 116 that is sometimes referred to as a transformer.Coupled inductor T1 116 is an energy transfer element in the examplepower converter of FIG. 1. Coupled inductor T1 116 includes a primarywinding 112 and a secondary winding 118. Primary winding 112 issometimes referred to as an input winding, and secondary winding 118 issometimes referred to as an output winding. In the example of FIG. 1,one end of secondary winding 118 is coupled to an output return 130. Inother examples, coupled inductor T1 116 may have additional windingscoupled to the output return 130, and additional windings coupled to theinput return 114. The additional windings coupled to the output return130 are sometimes referred to as output windings. Additional windingscoupled to the input return 114 are sometimes referred to as biaswindings, auxiliary windings, or primary sensing windings.

One end of primary winding 112 receives the dc voltage V_(BULK) 108 inthe example of FIG. 1. The other end of primary winding 112 is coupledto a switch SW1 146 that opens and closes in response to a drive signalfrom a controller 142. A clamp circuit 110 is coupled across the ends ofprimary winding 112 to protect the switch SW1 146 from excessive voltagethat may result from the switching of switch SW1 146.

In a practical power converter, switch SW1 146 is typically asemiconductor device such as for example a transistor that is controlledby a drive signal to be either open or closed. A switch that is opencannot conduct current. A switch that is closed may conduct current.

In the example of FIG. 1, switch SW1 146 receives a drive signal from adrive signal terminal 144 of controller 142. The drive signal changesperiodically between a high value and low value with period T_(S) thatis the switching period. The switching period T_(S) is much less thanthe ac line period T_(L). The switching period T_(S) is the reciprocalof the switching frequency. In one example, the switching period T_(S)is about 15 microseconds or less when the power converter is providingmaximum output power to load 128, whereas the ac line period T_(L) isabout 20 milliseconds. In other words, the ac line period T_(L) istypically more than 1000 times greater than the switching period T_(S),so that there can be typically more than 1000 switching periods withinone ac line period.

In the example power converter of FIG. 1, the switching of switch SW1146 produces pulsating currents in the primary winding 112 and in thesecondary winding 118 of coupled inductor T1 116. Current from secondarywinding 118 is rectified by diode D1 120 and filtered by an outputcapacitor C2 122 to produce an output voltage V_(O) 124 and an outputcurrent I_(O) 126. In the example of FIG. 1, output voltage V_(O) 124 ispositive with respect to an output return 130.

In the example of FIG. 1, the input return 114 is galvanically isolatedfrom the output return 130. Galvanic isolation prevents dc currentbetween input and output of the power converter. In other words, a dcvoltage applied between an input terminal and an output terminal of apower converter with galvanic isolation will produce substantially no dccurrent between the input terminal and the output terminal of the powerconverter. It is appreciated that in other examples, power converterswithout galvanic isolation may be used depending on system isolationrequirements and would still benefit from the teachings of the presentinvention.

In the example of FIG. 1, controller 142 receives an input voltage sensesignal at an input voltage sense terminal 140, an output voltage sensesignal at an output voltage sense terminal 148, and a current sensesignal at a current sense terminal 134 for the regulation of outputvoltage V_(O) 124. The voltages of controller 142 are referenced to theinput return 114. In various examples, the output voltage sense signalreceived at output voltage sense terminal 148 may be galvanicallyisolated from the output return 130 by the use of an optocoupler, or forexample by the use of a winding on a transformer, or for example by theuse of magnetically coupled conductors that are part of a leadframe ofan integrated circuit package, or for example by the use of special highvoltage safety capacitors.

A variety of different techniques may be utilized to sense the switchcurrent I_(SW1) 132 for the current sense signal at the current senseterminal 134. For example, the switch current I_(SW1) 132 may be sensedas a voltage on a discrete resistor, or as a current from a currenttransformer, or as a voltage across the on-resistance of a metal oxidesemiconductor field effect transistor (MOSFET) or as a current from thesense output of a current sensing field effect transistor (senseFET).

In the example of FIG. 1, the ac input voltage V_(AC) 102 is sensed asthe dc voltage V_(BULK) 108 on capacitor C1 106. The dc input voltageV_(BULK) 108 is coupled to an input sensing resistor R1 118 before it isreceived at the input voltage sense terminal 140 of controller 142.Current in resistor R1 returns to the ac input through the bridgerectifier 104.

FIG. 2 is a functional block diagram 200 of an example controller 202for the example power converter of FIG. 1 illustrating elements of aninput voltage sensor in accordance with the teachings of the presentinvention. In the example of FIG. 2, controller 202 is an integratedcircuit that includes a buffer amplifier 226, comparators 230, an ORgate 212, a high voltage transistor Q_(HV) 220, a current mirror formedby transistors 240 and 242, a monostable multivibrator 250 (also knownas a one-shot and a single shot), a logic inverter 208, a switch driver210, with various analog and digital circuits 234. In one example,buffer amplifier 226, high voltage transistor Q_(HV) 220, and thecurrent mirror formed by transistors 240 and 242 may be considered asbeing part of an input sense circuit included in controller 202. In oneexample, OR gate 212, monostable multivibrator 250 and logic inverter208 may be considered as being part of a sense enable circuit includedin controller 202.

The various analog and digital circuits 234 typically include anoscillator (not shown in FIG. 1) that provides signals available to allcircuits in controller 202 for synchronization and timing. In somecontrollers, signals for synchronization and timing may be received fromany suitable marker of time instead of an oscillator, such as forexample a system clock.

It will be appreciated by those skilled in the art that a powerconverter controller need not be entirely within an integrated circuit.For example, high voltage transistor Q_(HV) 220 may be a discretetransistor outside an integrated circuit, and other elements of thecontroller may be included in one or more integrated circuits.

In the example of FIG. 2, controller 202 receives an input voltage sensesignal at an input voltage sense terminal 140 that is coupled to one endof a voltage sensing resistor R1 118. The other end of the voltagesensing resistor R1 118 may be coupled to a rectified ac input voltage,for example V_(BULK) 108 shown in the example of FIG. 1. The inputvoltage sense terminal 140 of the example controller 202 in FIG. 2 is ahigh voltage terminal with respect to the input return 114. A highvoltage terminal of an integrated circuit is generally one that isadapted to withstand more than 30 volts with respect to the groundterminal without damage or disruption to the operation of the integratedcircuit. In the example of FIG. 2, the voltage at the input voltagesense terminal 140 may be as high as the peak of the rectified voltageV_(BULK) 108 that may exceed several hundred volts.

In the example of FIG. 2, the input voltage sense terminal 140 iscoupled to the drain D 218 of a high voltage transistor Q_(HV) 220. Inone example, high voltage transistor Q_(HV) 220 is an n-channelenhancement mode metal oxide semiconductor field effect transistor(MOSFET). In the example of FIG. 2 high voltage transistor Q_(HV) 220has a gate G 216 coupled to the output of an OR gate 212, and a source S222 coupled to the drain and gate of a low voltage MOSFET 240.

When high voltage transistor Q_(HV) 220 is in an ON state it may conductcurrent between drain and source. When high voltage transistor Q_(HV)220 is in an OFF state it cannot conduct current. A transistor in an ONstate may be considered to be a switch that is closed. A transistor inan OFF state may be considered to be a switch that is open. High voltagetransistor Q_(HV) 220 is in an ON state when the voltage at the gate G216 is greater than the voltage at the source S 222 by more than athreshold voltage V_(T). Conversely, high voltage transistor Q_(HV) 220is in an OFF state when the voltage at the gate G 216 is not greaterthan the voltage at the source S 222 by more than a threshold voltageV_(T). A transistor in an ON state is sometimes referred to as being ON.A transistor in an OFF state is sometimes referred to as being OFF.

In one example, the threshold voltage V_(T) of high voltage transistorQ_(HV) 220 is typically 2.5 volts. In one example, the output of OR gate212 is approximately 5.8 volts at a logic high level and the output ofOR gate 212 is substantially zero volts at a logic low level. In otherwords, high voltage transistor Q_(HV) 212 may conduct current when theoutput of OR gate 212 is at a high logic level, and the high voltagetransistor Q_(HV) 220 cannot conduct current when the output of OR gate212 is at a logic low level.

The output of OR gate 212 in the example of FIG. 2 determines when highvoltage transistor Q_(HV) 220 is ON and when high voltage transistorQ_(HV) 220 is OFF. When high voltage transistor Q_(HV) 220 in theexample controller of FIG. 2 is ON, the input sense circuit is enabledas the input voltage sense terminal 140 may receive current I_(R1) 224from the input through input sensing resistor R1 118. When high voltagetransistor Q_(HV) 220 is OFF, the input sense circuit is disabled inputvoltage sense terminal 140 receives substantially no current from theinput. In other words, controller 202 in the example of FIG. 2 isenabled to sense the input voltage only when high voltage transistorQ_(HV) 220 is ON. Controller 202 in the example of FIG. 2 reduces thepower consumed in sensing the input voltage to the power converter 100by limiting the times when input voltage sense terminal 140 receivescurrent from the input to the power converter in accordance with theteachings of the present invention.

High voltage transistor Q_(HV) 220 in the example of FIG. 2 may beconsidered an input voltage sense switch that closes to enable sensingof the input voltage, and that opens to disable sensing of the inputvoltage and prevent power consumption from the sensing of the inputvoltage in accordance with the teachings of the present invention.

When high voltage transistor Q_(HV) 220 in the example controller ofFIG. 2 is ON, a current I_(R1) 224 that is representative of the inputvoltage may enter the drain of transistor 240. Transistors 240 and 242form a current mirror with a ratio K that scales the current I_(R1) 224in the drain of transistor 240 to a mirrored current I_(MR1) 238 that isI_(R1) multiplied by K in the drain of transistor 242. As shown in thedepicted example, mirrored current I_(MR1) is processed by a bufferamplifier 226, which is coupled to produce a buffered sense signal 228.Buffer amplifier 226 in the example of FIG. 2 may provide amplification,level shifting, current-to-voltage conversion, and any othertransformation known in the art as needed to make the buffered sensesignal 228 compatible with the circuits that receive it, such as forexample comparators 230.

In the example controller 202 of FIG. 2, comparators 230 receive thebuffered sense signal 228 that is responsive to the input voltage of thepower converter. Buffered sense signal 228 is compared to thresholdvalues that correspond to the range of input voltage specified for thepower converter to operate. When enabled by a logic high level of SENSEENABLE signal 214 at a COMPARE ENABLE input 248, the comparators 230assert either an over-voltage signal 232 or an under-voltage signal 236if the input voltage is outside the specified range for operation. Inthe example of FIG. 2, the SENSE ENABLE signal 214 is at a logic lowlevel when the voltage sense circuit is disabled from sensing the inputvoltage to prevent the assertion of a false under-voltage signal.

In the example controller 202 of FIG. 2, analog and digital circuits 234receive and process control sense signals as required to regulate theoutput of the power converter. CURRENT SENSE signal 244, OUTPUT VOLTAGESENSE signal 246, OVER-VOLTAGE signal 232 and UNDER-VOLTAGE signal 236are processed to produce a command signal 252 that is received by aswitch driver circuit 210. Switch driver circuit 210 produces a DRIVEsignal 254 at drive terminal 144. DRIVE signal 254 goes to a logic highlevel to close switch SW1 146. DRIVE signal 254 goes to a logic lowlevel to open switch SW1 146. A timing diagram is presented later inthis disclosure to illustrate the relationships among various signals inthe example controller of FIG. 2.

Monostable multivibrator 250 in the example of FIG. 2 receives aninverted drive signal 206 from inverter 208 to produce a DRIVE EXTENDsignal 204 that is received at a first input of OR gate 212. In theexample of FIG. 2, DRIVE EXTEND signal 204 goes to logic high level whenDRIVE signal 254 goes to a logic low level. A second input of input ofOR gate 212 receives the DRIVE signal 254 to produce a SENSE ENABLEsignal 214 that is received at the gate G 216 of high voltage transistorQ_(HV) 220. High voltage transistor Q_(HV) 220 is ON when an input of ORgate 212 is at a logic high level.

FIG. 3 is a timing diagram 300 that shows example waveforms illustratingthe operation of the example input voltage sensor shown in FIG. 2 asused in the example power converter of FIG. 1. The example waveforms ofFIG. 3 are for steady-state conditions after transient disturbances fromthe application of ac input voltage V_(AC) 102 have decayed tonegligible values.

Waveform 305 in the example of FIG. 3 represents the current I_(SW1) 132in the switch SW1 146 of the example power converter of FIG. 1. CurrentI_(SW1) 132 increases linearly while switch SW1 146 is ON in the examplepower converter of FIG. 1, and current I_(SW1) is substantially zerowhen switch SW1 146 is OFF.

Waveform 310 in the example of FIG. 3 represents DRIVE signal 254 in theexample controller of FIG. 2 that drives switch SW1 146 in the examplepower converter of FIG. 1. The waveforms of FIG. 3 show that switch SW1146 is ON when DRIVE signal 254 is at a logic high level, and switch SW1146 is OFF when DRIVE signal 254 is at a logic low level.

Waveform 315 in the example of FIG. 3 represents the DRIVE EXTEND signal204 in the example controller of FIG. 2. Waveform 320 in the example ofFIG. 3 represents the SENSE ENABLE signal 214 in the example controllerof FIG. 2. Since the SENSE ENABLE signal 214 is the output of an OR gate212 that receives DRIVE signal 254 with DRIVE EXTEND signal 204, theSENSE ENABLE signal 214 is at a logic high level when either DRIVEEXTEND signal 204 or SENSE ENABLE signal 214 is at a logic high level.

The timing diagram 300 of FIG. 3 shows waveforms of signals from theexample power converter 100 of FIG. 1 that uses the example controller200 of FIG. 2 for the condition of a light load (low output current)before time t₆ and for the condition of a moderate to heavy load (higheroutput current) after time t₆. For the condition of a light load on thepower converter, the switching period is T_(S1) as indicated by theseparation between times t₀ and t₃ that mark the times when the switchSW1 146 turns ON. Similarly for the condition of a moderate to heavyload, the switching period is T_(S2) as indicated by the separationbetween times t₆ and t₈, and the separation between times t₈ and t₁₁.

The timing diagram of FIG. 3 illustrates that the switching periodT_(S1) for a light load is generally substantially greater than theswitching period T_(S2) for a moderate to heavy load in the examplepower converter of FIG. 1. It is a common practice in the design ofcontrollers for power converters to increase the switching period(reduce the switching frequency) under conditions of light loading toreduce losses attributed to switching events, particularly for powerconverters that must operate with high efficiency at light loads. Aswitching period greater than a threshold value may therefore indicatethe presence of a light load and the need to sense the input voltagewith reduced power consumption.

In the example of FIG. 3, switch SW1 146 is ON for the duration T_(ON)between times t₀ and t₁, between times t₃ and t₄, between times t₆ andt₇, between times t₈ and t₁₀, and between times t_(ii) and t₁₃. To avoidunnecessary complexity in the illustration, FIG. 3 shows the durationthat the switch SW1 146 is ON is the same in each switching period forthe condition of light load and for the condition of moderate to heavyload, indicating that the input voltage is the same for both conditionsin the example of FIG. 3. The input voltage to the power converter andthe duration T_(ON) that the switch SW1 146 remains ON may be differentin each switching period. In one example, the duration T_(ON) that theswitch SW1 146 remains ON is approximately 7 microseconds.

As shown in the example timing diagram of FIG. 3, the switching periodis the sum of an on-time and an off-time of switch SW1 146. For thelight load condition, the off-time is T_(OFF1) between times t₁ and t₃.For the moderate to heavy load condition, the off-time is T_(OFF2)between times t₇ and t₈, and between times t₁₀ and t₁₁.

The example of FIG. 3 shows that a high to low transition of the DRIVEsignal 254 initiates a low to high transition of the DRIVE EXTEND signal204 from the monostable multivibrator 250. The DRIVE EXTEND signal 204remains at a logic high level for an extended duration T_(EX) afterswitch SW1 146 turns OFF, as shown in the timing diagram between timest₁ and t₂, between times t₄ and t₅, between times t₇ and t₉, and betweentimes t₁₀ and t₁₂. The design of monostable multibibrator 250 sets theextended duration T_(EX).

The timing diagram of FIG. 3 shows that the SENSE ENABLE signal 214 isat a logic high level when the DRIVE signal 254 signal is at a logichigh level. Therefore, the controller senses the input voltage wheneverthe switch SW1 146 is conducting. After the switch SW1 146 turns OFF,the DRIVE EXTEND signal 204 keeps the SENSE ENABLE signal 214 at a logichigh level, allowing the controller to continue sensing the inputvoltage for the extended duration T_(EX) after the switch SW1 146 turnsOFF. If the off-time of the switch SW1 146 exceeds T_(EX), then theSENSE ENABLE signal 214 goes to a logic low level that prevents thecontroller from sensing the input voltage, reducing the power consumedby the input sense circuit. The timing diagram of FIG. 3 shows that thecontroller does not sense the input voltage during the time T_(VSOFF)between times t₂ and t₃.

If the off-time of switch SW1 146 is less than the extended durationT_(EX), then the SENSE ENABLE signal 214 remains high for the entireswitching period as illustrated after time t₆, and the controller sensesthe input voltage continuously without interruption. In other words, thecontroller senses the input voltage continuously when the load on thepower converter is moderate to heavy, but the controller senses theinput voltage only during a fraction of a switching period when the loadon the power converter is light.

At moderate to heavy loads, the power consumed by sensing the inputvoltage is negligible in comparison to other losses in the powerconverter. At light loads where the power consumed by sensing the inputvoltage is a significant part of the total loss in the power converter,the input voltage is sensed for only a fraction of the switching period.The voltage on the switch SW1 is highest when the switch makes thetransition from ON to OFF. At any given input voltage, the voltage thatappears on the switch SW1 146 when the switch turns off at moderate toheavy loads is higher than the voltage that appears on the switch SW1146 when the switch turns off at light loads. Therefore, at light loadsthe converter is less likely to be damaged from an excessive inputvoltage, and the risk is relatively low that the input voltage will gethigh enough to damage the converter between sensing events. At moderateto heavy loads, however, it is important to sense the input voltagecontinuously so that the controller may prevent the switch from turningON when the input voltage is too high.

FIG. 4 is a graph 400 that illustrates the relationships betweenoff-time T_(OFF), extended duration T_(EX), and the duration of no linesensing T_(VSOFF). The graph shows that the duration of no line sensingT_(VSOFF) is zero when the off-time of switch SW1 146 is less than orequal to the extended duration T_(EX). The graph also shows that theduration of no line sensing T_(VSOFF) increases from zero with aconstant slope when the off-time of switch SW1 146 is greater than theextended duration T_(EX). In one example, the extended duration T_(EX)is 50 microseconds because the off-time of switch SW1 146 at moderateloads in that example is also about 50 microseconds. In the sameexample, the off-time of switch SW1 146 at light loads (where there is aneed to sense the input voltage with reduced power consumption) may beapproximately 50 milliseconds, about 1000 times longer than the off-timeat moderate loads.

FIG. 5 is a functional block diagram 500 of an example controller 502for the power converter in FIG. 1 illustrating elements of analternative input voltage sensor in accordance with the teachings of thepresent invention. FIG. 5 includes many of the elements illustrated inthe example of FIG. 2.

In the alternative example of FIG. 5, the gate G 216 of high voltagetransistor Q_(HV) 220 is coupled to a regulated internal voltage V_(DD)504, and the source S 222 of high voltage transistor Q_(HV) 220 iscoupled to the drain of a low voltage transistor Q_(LV) 520. In oneexample, the regulated internal voltage V_(DD) 504 is approximately 5.8volts. The source of low voltage transistor Q_(LV) 520 is coupled totransistor 240 of the current mirror as in FIG. 2.

In the alternative example of FIG. 5, OR gate 212 produces a SENSEENABLE signal 214 that is coupled to the gate of low voltage transistorQ_(LV) 520 and is received by the comparators 230 at a COMPARE ENABLEinput 248. When SENSE ENABLE signal 214 is a logic high level(approximately V_(DD)), low voltage transistor Q_(LV) 520 turns ONenabling controller 502 to sense the input voltage as current I_(R1)224. When SENSE ENABLE signal 209 is a logic low level (approximatelyzero volts), low voltage transistor Q_(LV) 520 turns OFF disablingcontroller 502 from sensing the input voltage and preventing controller502 from receiving current from the input voltage in accordance with theteaching of the present invention.

Low voltage transistor Q_(LV) 520 in the alternative example of FIG. 5may be considered a line sense switch that closes to allow sensing ofthe input voltage to the power converter, and that opens to stop thesensing circuit from consuming power from the input voltage to the powerconverter.

FIG. 6 is a functional block diagram 600 of another example controller602 for the example power converter in FIG. 1 illustrating elements ofanother alternative input voltage sensor in accordance with theteachings of the present invention. FIG. 6 includes many of the elementsillustrated in the examples of FIG. 2 and FIG. 5.

The alternative example of FIG. 6 replaces the MOSFET that is highvoltage transistor Q_(HV) 220 in FIG. 5 with an n-channel junction fieldeffect transistor (JFET) Q_(HV) 620. Whereas the gate G 216 of the highvoltage MOSFET Q_(HV) 220 in FIG. 5 is coupled to the regulated internalvoltage V_(DD) 504, the gate G 616 of high voltage JFET Q_(HV) 620 inFIG. 6 is coupled to the input return 114.

The drain D 618 of high voltage transistor Q_(HV) 620 in the alternativeexample of FIG. 6 is coupled to the input voltage sense terminal 140,and the source S 622 of high voltage JFET Q_(HV) 620 is coupled to lowvoltage transistor Q_(LV) 520. As such, JFET Q_(HV) 620 in the exampleof FIG. 6 performs the same function as MOSFET Q_(HV) 220 in FIG. 5.JFET Q_(HV) 620 in the example of FIG. 6 is ON when low voltagetransistor Q_(LV) 520 is ON and the input sense circuit is enabled tosense the input voltage, and JFET Q_(HV) 620 in the example of FIG. 6 isOFF when low voltage transistor Q_(LV) 520 is OFF and the input sensecircuit is disabled from sensing the input voltage.

FIG. 7 is a flow diagram 700 that illustrates an example process for apower converter controller that senses an input voltage in accordancewith the teachings of the present invention. The example flow diagram ofFIG. 7 is consistent with the example controller of FIG. 2 and with theexample waveforms of FIG. 3. After starting in block 705 with inputvoltage applied to the power converter and the controller has determinedthat the input voltage is within the proper limits for the converter tooperate, the controller closes a power switch in block 710 to begin anon-time T_(ON). The controller also closes a line sense switch in block715 to begin input voltage sensing by allowing the controller to receivecurrent at an input voltage sense terminal.

After the line sense switch closes in block 715, the controllerprocesses control sense signals such as for example current sense,output sense, over-voltage sense, and under-voltage sense signals inblock 720. When the processing calls for the power switch to turn OFF,the off-time T_(OFF) of the power switch begins in block 725. Theextended input voltage sensing duration T_(EX) begins in block 730 whenthe power switch turns OFF.

The controller continues to process the control sense signals in block740, while the off-time T_(OFF) increases in decision block 750. If theoff-time T_(OFF) exceeds the extended input voltage sensing durationT_(EX), then the extended input sensing duration T_(EX) ends in block745, the input voltage sensing ends in block 735, and the flow continuesto blocks 775 and 780 where the controller processes the control sensesignals until the controller ends the off-time and another on-timeT_(ON) begins in block 710. If the off-time T_(OFF) does not exceed theextended input voltage sensing duration T_(EX), then the flow continuesto block 755. The off-time T_(OFF) increases in blocks 755 and 760 untilthe controller ends the off-time and another on-time T_(ON) begins inblock 765, followed by the end of the extended input voltage sensingduration T_(EX) in block 770. The processing of control sense signalscontinues in block 720.

Some applications of power converters require the input capacitor C1 106to be large enough for the power converter to provide a regulated outputto a heavy load for a time equivalent to several ac line periods afterthe ac input is removed. In these applications, when the load is verylight or near zero load the dc input voltage V_(BULK) 108 may requiretens of seconds to decay below a minimum threshold value after the acinput voltage V_(AC) 102 is removed. A power converter controller thatmust detect an input under-voltage condition within a few periods of theac input voltage is therefore unable to do so reliably from only ameasurement of the bulk voltage V_(BULK) 108. For these applications,the controller may sense the ac input voltage as illustrated by theexample of FIG. 8.

FIG. 8 is a schematic diagram 800 of an example power converterincluding a controller that senses a switching voltage V_(SW) 852 thatis representative of the dc input voltage V_(BULK) 108 in addition tosensing the ac input voltage V_(AC) 102 in accordance with the teachingsof the present invention. In the example power converter of FIG. 8, oneend of voltage sensing resistor R1 118 is coupled to neutral inputterminal N 152 to receive a half-wave rectified voltage V_(RECT) 850. Inanother example, one end of voltage sensing resistor R1 118 may becoupled to line input terminal L 150 to receive a half-wave rectifiedvoltage V_(RECT) 850.

Controller 842 in the example converter of FIG. 8 may sense the ac inputvoltage V_(AC) 102 continuously when the load on the power converter ismoderate to heavy, and it may sense the ac input voltage V_(AC) 102 onlyduring a fraction of a switching period when the load on the powerconverter is light according to the teaching of the present invention,in the same way that the converter of FIG. 1 senses the dc input voltageV_(BULK) 108.

Circuits in controller 842 may respond to the absence of ac inputvoltage for more than one ac line period. Circuits in controller 842 maydetect either an over-voltage condition or an under-voltage condition bysensing a switching voltage that is proportional to the bulk voltageV_(BULK) 108.

A switching voltage V_(SW) 852 that is proportional to the bulk voltageV_(BULK) 108 is available at the output winding 118 of the example powerconverter of FIG. 8. Since the magnitude of the switching voltage V_(SW)852 is a substantially lower voltage than the peak of the ac inputvoltage V_(AC) 102, the controller may sense the switching voltageV_(SW) 852 with significantly lower power consumption than would berequired to sense the higher voltage V_(BULK) 108.

The example power converter of FIG. 8 is obtained from the example ofFIG. 1 by relocating output diode D1 120 of FIG. 1 to the position ofoutput diode D2 820 of FIG. 8, and by receiving the switching voltageV_(SW) 852 with a modified controller 842. An isolation circuit 856provides galvanic isolation between the input return 114 and the outputreturn 130 such that the switching voltage sense signal 858 isgalvanically isolated from the switching voltage signal 854.

In one example, isolation circuit 856 may be an optocoupler. In anotherexample, isolation circuit 856 may include a transformer. With themodifications illustrated in FIG. 8, the modified controller 846 maydetect an input over-voltage condition even when the controller is notreceiving current from the ac input voltage V_(AC) 102. It isappreciated that in other examples, a switching voltage signal analogousto switching voltage V_(SW) 852 could be obtained from a separatewinding other than the output winding 118 shown in FIG. 8 while stillbenefiting from the teachings of the present invention.

Every conductor in an electrical circuit has a finite parasiticcapacitance that may store an electric charge. Leakage currents intypical applications usually discharge the parasitic capacitance fastenough to make the effects of the parasitic capacitance negligible. Inapplications where the effects of parasitic capacitance are notnegligible, relatively small modifications to the example circuits mayallow those applications to benefit from the ac voltage sensor with lowpower consumption in accordance with the teachings of the presentinvention. FIG. 9 is a schematic diagram 900 of an example powerconverter controller 902 illustrating elements of an input voltagesensor that includes an optional element to discharge stray capacitanceat an input voltage sense terminal in accordance with the teachings ofthe present invention.

The example controller of FIG. 9 includes many of the elementsillustrated in the example of FIG. 6. Parasitic capacitance 905 betweeninput voltage sense terminal 140 and input return 114 may charge to theinput voltage when high voltage transistor Q_(HV) 620 is not conducting.The discharge of parasitic capacitance 905 through low voltagetransistor Q_(LV) 520 might produce a high value for current I_(R1) 224that would indicate a false high input voltage to the controller. Toprevent false indications of high input voltage, the parasiticcapacitance 905 may be discharged through a path that does not put thecurrent from the discharge of the capacitance through transistor 240 ofthe current mirror formed by transistors 240 and 242. In the example ofFIG. 9, the stray capacitance 905 is discharged through transistorQ_(CD) 910 in response to a DISCHARGE signal 915. In one example,circuits in the controller (not shown in FIG. 9) raise DISCHARGE signal915 to a high logic level for about 200 nanoseconds to discharge straycapacitance 905 immediately before DRIVE signal 254 goes high.

The above description of illustrated examples of the present invention,including what is described in the Abstract, are not intended to beexhaustive or to be limitation to the precise forms disclosed. Whilespecific embodiments of, and examples for, the invention are describedherein for illustrative purposes, various equivalent modifications arepossible without departing from the broader spirit and scope of thepresent invention. Indeed, it is appreciated that the specific examplevoltages, currents, frequencies, power range values, times, etc., areprovided for explanation purposes and that other values may also beemployed in other embodiments and examples in accordance with theteachings of the present invention.

What is claimed is:
 1. A power converter controller, comprising: aswitch driver circuit coupled to generate a drive signal to controlswitching of a power switch to control a transfer of energy from aninput of the power converter to an output of the power converter; aninput sense circuit to receive an input sense signal representative ofthe input of a power converter; and a sense enable circuit coupled toreceive the drive signal to generate a sense enable signal to controlthe input sense circuit in response to the drive signal, wherein thesense enable signal is coupled to control the input sense circuit tosense the input sense signal continuously in response to a first loadcondition at the output of the power converter, and wherein the senseenable signal is coupled to control the input sense circuit to sense theinput sense signal only during a fraction of a switching period of thepower switch in response to a second load condition at the output of thepower converter.
 2. The power converter controller of claim 1 furthercomprising a comparator circuit coupled to the input sense circuit andthe sense enable circuit, wherein the comparator is coupled to detect ifthe input of the power converter is greater or less than one or morethresholds.
 3. The power converter controller of claim 2 wherein the oneor more thresholds include one or more of an under-voltage threshold andan over-voltage threshold.
 4. The power converter controller of claim 1wherein the input sense circuit is a current input sense circuit, andwherein the input sense signal representative of the input of the powerconverter is a current.
 5. The power converter controller of claim 1wherein input sense circuit comprises a high voltage transistor coupledto receive the input sense signal.
 6. The power converter controller ofclaim 5 wherein the input sense circuit further comprises a low voltagetransistor coupled to the high voltage transistor, wherein the lowvoltage transistor is coupled to be switched in response to the senseenable signal.
 7. The power converter controller of claim 5 wherein thehigh voltage transistor is coupled to be switched in response to thesense enable signal.
 8. The power converter controller of claim 1wherein the input sense circuit comprises a current mirror circuitcoupled to receive the input sense signal representative of the input ofthe power converter, wherein the current mirror circuit is coupled togenerate a scaled representation of the input sense signal.
 9. The powerconverter controller of claim 8 wherein the input sense circuit furthercomprises a buffer amplifier circuit coupled to the current mirrorcircuit, wherein the buffer amplifier circuit is coupled to output thescaled representation of the input sense signal.
 10. The power convertercontroller of claim 1 wherein the sense enable circuit comprises amonostable multivibrator coupled to generate a drive extend signal inresponse to the drive signal, wherein the sense enable circuit isfurther coupled to generate the sense enable signal to control the inputsense circuit in response to the drive extend signal.
 11. The powerconverter controller of claim 10 wherein the sense enable circuitfurther comprises an OR gate coupled to generate the sense enable signalin response to the drive signal and drive extend signal.
 12. The powerconverter controller of claim 1 wherein the switching period of thepower switch in response to the second load condition at the output ofthe power converter is greater than a switching period of the powerswitch in response to the first load condition at the output of thepower converter.
 13. The power converter controller of claim 1 whereinthe first load condition at the output of the power converter is aheavier load condition than the second load condition at the output ofthe power converter.
 14. A power converter, comprising: an energytransfer element coupled between an input of the power converter and anoutput of the power converter; a power switch coupled to the input ofthe power converter and the energy transfer element; and a powerconverter controller coupled to generate a drive signal coupled tocontrol switching of the power switch to control a transfer of energyfrom the input of the power converter to the output of the powerconverter in response to a feedback signal representative of the outputof the power converter, wherein the power converter controller includes:a switch driver circuit coupled to generate the drive signal to controlswitching of the power switch to control the transfer of energy from theinput of the power converter to the output of the power converter; aninput sense circuit to receive an input sense signal representative ofthe input of a power converter; and a sense enable circuit coupled toreceive the drive signal to generate a sense enable signal to controlthe input sense circuit in response to the drive signal, wherein thesense enable signal is coupled to control the input sense circuit tosense the input sense signal continuously in response to a first loadcondition at the output of the power converter, and wherein the senseenable signal is coupled to control the input sense circuit to sense theinput sense signal only during a fraction of a switching period of thepower switch in response to a second load condition at the output of thepower converter.
 15. The power converter of claim 14 wherein the powerconverter controller is coupled to receive a current sense signalrepresentative of a current through the power switch, wherein the powerconverter controller is further coupled to generate the drive signalcoupled to control switching of the power switch to control the transferof energy from the input of the power converter to the output of thepower converter in response to current sense signal.
 16. The powerconverter of claim 14 wherein the power converter controller furtherincludes a comparator circuit coupled to the input sense circuit and thesense enable circuit, wherein the comparator is coupled to detect if theinput of the power converter is greater or less than one or morethresholds.
 17. The power converter of claim 16 wherein the one or morethresholds include one or more of an under-voltage threshold and anover-voltage threshold.
 18. The power converter of claim 14 wherein theinput sense circuit is a current input sense circuit, and wherein theinput sense signal representative of the input of the power converter isa current.
 19. The power converter of claim 14 wherein input sensecircuit comprises a high voltage transistor coupled to receive inputsense signal.
 20. The power converter of claim 19 wherein input sensecircuit further comprises a low voltage transistor coupled to the highvoltage transistor, wherein the low voltage transistor is coupled to beswitched in response to the sense enable signal.
 21. The power converterof claim 19 wherein the high voltage transistor is coupled to beswitched in response to the sense enable signal.
 22. The power converterof claim 14 wherein the input sense circuit comprises a current mirrorcircuit coupled to receive the input sense signal representative of theinput of the power converter, wherein the current mirror circuit iscoupled to generate a scaled representation of the input sense signal.23. The power converter of claim 22 wherein the input sense circuitfurther comprises a buffer amplifier circuit coupled to the currentmirror circuit, wherein the buffer amplifier circuit is coupled tooutput the scaled representation of the input sense signal.
 24. Thepower converter of claim 14 wherein the sense enable circuit comprises amonostable multivibrator coupled to generate a drive extend signal inresponse to the drive signal, wherein the sense enable circuit isfurther coupled to generate the sense enable signal to control the inputsense circuit in response to the drive extend signal.
 25. The powerconverter of claim 24 wherein the sense enable circuit further comprisesan OR gate coupled to generate the sense enable signal in response tothe drive signal and drive extend signal.
 26. The power converter ofclaim 14 wherein the switching period of the power switch in response tothe second load condition at the output of the power converter isgreater than a switching period of the power switch in response to thefirst load condition at the output of the power converter.
 27. The powerconverter of claim 14 wherein the first load condition at the output ofthe power converter is a heavier load condition than the second loadcondition at the output of the power converter.